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SS6341 数据表(PDF) 11 Page - Silicon Standard Corp.

部件名 SS6341
功能描述  High Performance, Triple-Output, Auto-Tracking Combo Controller
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制造商  SSC [Silicon Standard Corp.]
网页  http://www.siliconstandard.com
标志 SSC - Silicon Standard Corp.

SS6341 数据表(HTML) 11 Page - Silicon Standard Corp.

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SS6341
After the initial transient, the ESL dependent term drops
off. Because of the strong relationship between output
capacitor ESR and output load transient, the output
capacitor is usually chosen for ESR, not for capacitance
value. A capacitor with suitable ESR will usually have a
larger capacitance value than is needed for energy
storage.
A common way to lower ESR and raise ripple current
capability is to parallel several capacitors. In most case,
multiple electrolytic capacitors of small case size are
better than a single large case capacitor.
Output Inductor Selection
The inductor value and type should be chosen based on
output slew rate requirement, output ripple requirement
and expected peak current, and is primarily controlled by
the required current response time. The SS6341 will
provide either 0% or 85% duty cycle in response to a load
transient. The response time to a transient is different for
the application of load and remove of load.
t
L
I
V
V
RISE
OUT
IN
OUT
=
×
,
t
=
L
I
V
FALL
OUT
OUT
× ∆
where
∆IOUT is transient load current step.
In a typical 5V input, 2V output application, a 3
µH
inductor has a 1A/
µS rise time, resulting in a 5µS delay in
responding to a 5A load current step. To optimize
performance, different combinations of input and output
voltage and expected loads may require different inductor
values. A smaller value of inductor will improve the
transient response at the expense of increased output
ripple voltage and inductor core saturation rating.
Peak current in the inductor will be equal to the maximum
output load current plus half of inductor ripple current. The
ripple current is approximately equal to:
I
=
(V
V
)
V
L
V
RIPPLE
IN
OUT
OUT
IN
×
× ×
f
where f = 200KHz oscillator frequency.
The inductor must be able to withstand peak current
without saturation, and the copper resistance in the
winding should be kept as low as possible to minimize
resistive power loss
Input Capacitor Selection
Most of the input supply current is supplied by the input
bypass capacitor, and the resulting RMS current flow in
the input capacitor will heat it up. Use a mix of input bulk
capacitors to control the voltage overshoot across the
upper MOSFET. The ceramic capacitance for the high
frequency decoupling should be placed very close to the
upper MOSFET to suppress the voltage induced in the
parasitic circuit impedance. The buck capacitors to
supply the RMS current are approximate equal to:
I
(1 D)
D
I
1
12
V
D
f L
RMS
2
OUT
IN
2
= −
×
×
+
×
×
×


where
D
V
V
OUT
IN
=
The capacitor voltage rating should be at least 1.25 times
greater than the maximum input voltage.
PWM MOSFET Selection
In high current PWM application, the MOSFET power
dissipation, package type and heatsink are the dominant
design
factors.
The
conduction
loss
is
the
only
component of power dissipation for the lower MOSFET,
since it turns on into near zero voltage. The upper
MOSFET has conduction loss and switching loss. The
gate charge losses are proportional to the switching
frequency and are dissipated by the SS6341.
However, the gate charge increases the switching
interval, tSW, which increase the upper MOSFET
switching losses. Ensure that both MOSFETs are within
their maximum junction temperature at high ambient
temperature
by
calculating
the
temperature
rise
according to package thermal resistance specifications.
P
I
R
D
I
V
t
f
2
UPPER
OUT
2
DS(ON)
OUT
IN
SW
=
×
× +
×
×
×
P
I
R
D)
LOWER
OUT
2
DS(ON)
=
×
× −
(1
The equations above do not model the power loss from the
reverse recovery of the lower MOSFET’s body diode.
The RDS(ON) is different for the two previous equations
Rev.2.01 6/26/2003


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