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MC33067DWR2 数据表(PDF) 11 Page - ON Semiconductor

部件名 MC33067DWR2
功能描述  High Performance Resonant Mode Controllers
Download  16 Pages
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制造商  ONSEMI [ON Semiconductor]
网页  http://www.onsemi.com
标志 ONSEMI - ON Semiconductor

MC33067DWR2 数据表(HTML) 11 Page - ON Semiconductor

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MC34067, MC33067
http://onsemi.com
11
Fault
Latch
S
R
Q
Figure 20. Fault Detector and Soft−Start
CSoft−Start
Fault
Input
10
9.0
mA
1.0 V
11
6
Ground
Soft−Start
Buffer
Error Amp
Clamp
UVLO + Fault
UVLO
Fault
Comparator
Fault
Soft−Start Circuit
The Soft−Start circuit shown in Figure 20 forces the
variable frequency Oscillator to start at the maximum
frequency and ramp downward until regulated by the
feedback control loop. The external capacitor at the
CSoft−Start terminal is initially discharged by the
UVLO+Fault signal. The low voltage on the capacitor
passes through the Soft−Start Buffer to hold the Error
Amplifier output low. After UVLO+Fault switches to a
logic zero, the soft−start capacitor is charged by a 9.0
mA
current source. The buffer allows the Error Amplifier output
to follow the soft−start capacitor until it is regulated by the
Error Amplifier inputs. The soft−start function is generally
applicable to controllers operating below resonance and can
be disabled by simply opening the CSoft−Start terminal.
APPLICATIONS INFORMATION
The MC34067 is specifically designed for zero voltage
switching
(ZVS)
quasi−resonant
converter
(QRC)
applications. The IC is optimized for double−ended
push−pull or bridge type converters operating in continuous
conduction mode. Operation of this type of ZVS with
resonant properties is similar to standard push−pull or bridge
circuits in that the energy is transferred during the transistor
on−time. The difference is that a series resonant tank is
usually introduced to shape the voltage across the power
transistor prior
to turn−on. The resonant tank in this
topology is not used to deliver energy to the output as is the
case with zero current switch topologies. When the power
transistor is enabled the voltage across it should already be
zero, yielding minimal switching loss. Figure 21 shows a
timing diagram for a half−bridge ZVS QRC. An application
circuit is shown in Figure 22. The circuit built is a dc to dc
half−bridge converter delivering 75 W to the output from a
48 V source.
When building a zero voltage switch (ZVS) circuit, the
objective is to waveshape the power transistor’s voltage
waveform so that the voltage across the transistor is zero
when the device is turned on. The purpose of the control IC
is to allow a resonant tank to waveshape the voltage across
the power transistor while still maintaining regulation. This
is accomplished by maintaining a fixed deadtime and by
varying the frequency; thus the effective duty cycle is
changed.
Primary side resonance can be used with ZVS circuits. In
the application circuit, the elements that make the resonant
tank are the primary leakage inductance of the transformer
(LL) and the average output capacitance (COSS) of a power
MOSFET (CR).
The desired resonant frequency for the application circuit
is calculated by Equation 6:
L L 2CR
1
=
π
2
ƒr
(eq. 6)
In the application circuit, the operating voltage is low and
the value of COSS versus Drain Voltage is known. Because
the COSS of a MOSFET changes with drain voltage, the
value of the CR is approximated as the average COSS of the
MOSFET. For the application circuit the average COSS can
be calculated by Equation 7:
measured at
CR
1
2
2 * COSS
=
in
V
(eq. 7)
The MOSFET chosen fixes CR and that LL is adjusted to
achieve the desired resonant frequency.
However, the desired resonant frequency is less critical
than the leakage inductance. Figure 21 shows the primary
current ramping toward its peak value during the resonant
transition. During this time, there is circulating current
flowing
through
the
secondary
inductance,
which
effectively makes the primary inductance appear shorted.
Therefore, the current through the primary will ramp to its
peak value at a rate controlled by the leakage inductance and
the applied voltage. Energy is not transferred to the
secondary during this stage, because the primary current has
not overcome the circulating current in the secondary. The
larger the leakage inductance, the longer it takes for the
primary current to slew. The practical effect of this is to
lower the duty cycle, thus reducing the operating range.


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